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u4311b-fs preliminary information rev. a2, 22-sep-98 1 (13) low-current superhet remote-control receiver description the u4311b is a monolithic integrated circuit in bipolar technology for low-current uhf remote control super-heterodyne receivers in amplitude- or frequency- modulated mode. typical applications are keyless car lock-, alarm- or tele-control remote indication systems. especially for automotive applications, it supports a superhet design with about 1 ma total current consumption as required by the car manufacturers. features usable for amplitude- and frequency-modulated transmission systems extremely low quiescent current (approximately 1 ma in standby mode due to wake-up concept) wide power supply voltage range 3 to 13 v sensitive if amplifier for 10.7-mhz operating frequency logarithmic am demodulator fm demodulator monoflop output to wake up a microcontroller high-performance operational amplifier to realize a data recovering filter non-inverting clamping comparator with amplitude- depending hysteresis for data regeneration block diagram non invert. clamping comparator monoflop bandgap quadrature detector operational amplifier if amplifier internal rf level wake up 13 3 wake-up out 97 v s 2 6 + 20 1 18 16 11 data out data filter fm out log am out 10.7 mhz 10.7 mhz 17 15 v ref = 2.4v 5 12648 v ref = 2.4 v 12 19 figure 1. block diagram ordering information extended type number package remarks u4311b-cfs sso20 ambient temperature up to +105 c
u4311b-fs rev. a2, 22 sep-98 preliminary information 2 (13) pin description 1 2 3 4 5 6 7 8 10 9 19 18 17 16 14 15 13 12 11 20 n.c. gnd2 12649 comp out rc n.c. rc+ op out rc wake v ref discr gnd1 n.c. sw out if in v s fm out n.c. am out op in+ op in figure 2. pinning pin symbol function 1 op in+ op amplifier non-inverted input 2 op out op amplifier output 3 rc wake rc wakeup reset time 4 n.c. not connected 5 gnd2 ground of the logical circuits 6 comp out comparator output 7 rc comparator time constant 8 n.c. not connected 9 rc+ comparator time constant 10 n.c. not connected 11 am out am current output 12 if in if input 13 sw out wake-up output 14 n.c. not connected 15 gnd1 ground of the analog circuits 16 discr fm discriminator tank 17 v ref reference voltage 18 fm out fm discriminator output 19 v s supply voltage 20 op in op amplifier inverted input internal connections see figures 4 to 19 absolute maximum ratings parameters symbol value unit supply voltage v s 13 v power dissipation t amb = 85 c p tot 400 mw junction temperature t j 125 c storage temperature t stg 55 to +125 c ambient temperature for sso20 t amb 40 to +105 c thermal resistance parameters symbol value unit junction ambient sso20 r thja 140 k/w
u4311b-fs preliminary information rev. a2, 22-sep-98 3 (13) electrical characteristics v s = 5 v, t amb = 25 c, f in = 10.7 mhz; fm part: f mod = 1 khz, f dev = 22.5 khz; am part: f mod = 1 khz, m = 100% unless otherwise specified parameters test conditions / pins symbol min. typ. max. unit characteristics supply-voltage range pin 19 v s 3 12 v quiescent supply current pin 19 i q 1 1.3 ma active supply current pin 19 i act 2.8 3.6 ma bandgap regulated voltage pin 17 v ref 2.3 2.4 2.5 v output current pin 17 i ref 5 ma source resistance pin 17 r ref 2.3 5 external capacitor pin 17 c ref 10 f power-supply rejection ratio f = 50 hz pin 17 psrr 60 db if amplifier input resistance pin 12 r in 180 330 520 input capacitance pin 12 c in 5 pf typical internal 3 db frequency if level 70 db v pins 12 and 18 f 3db 8 12 mhz 3 db limiting point pin 12 v fm3db 30 db v recovered data voltage pin 18 v fmout 50 130 230 mv fm detector output resistance pin 18 r fmout 50 k am rejection ratio m = 30% pins 12 and 18 am rr 25 db maximum am input voltage pin 12 v ammax 90 db v am quiescent current pin 11 i amout 10 22 37 maximum am current pin 11 i amoutmax 100 operational amplifier gain-bandwidth product pins 1, 2 and 20 f t 3 4 6.5 mhz excess phase pins 1, 2 and 20 80 degree open loop gain pins 1, 2 and 20 g 0 50 70 95 db output voltage range pin 2 d v out 1.55 v common mode input voltage pins 1 and 20 v in 0.7 1.7 v input offset voltage pins 1 and 20 v os 2.5 0 +2.5 mv maximum output current pin 2 i out 5 ma common-mode rejection ratio pin 1 and 20 cmrr 65 85 db total harmonic distortion v in < 300 mv, f = 33 khz, unity gain circuit pin 2 thd 1 3 % power-supply rejection ratio f = 50 hz pin 2 psrr 65 85 db
u4311b-fs rev. a2, 22 sep-98 preliminary information 4 (13) unit max. typ. min. symbol test conditions / pins parameters clamping comparator typical common-mode input voltage range pin 2 v cmvr 0.8 1.6 v maximum distortion voltage v signal = 100 mv, r+ = r = 50 k , c+ = c = 200 nf, f disto = 50 hz, f signal = 1 khz pin 2 v dmax 200 mv output voltage v 2 > (v 7 + v 9 ) /2 (10-k load to v ref ) pin 6 v cout v ref v 1) output voltage v 2 < (v 7 + v 9 ) /2 (10-k load to v ref ) pin 6 v cout 0 150 250 mv wake-up circuit minimum wake-up level pin 12 v in 40 db v 2) internal charging resistor pin 3 r int 1.5 k threshold voltage pin 3 v th 1.6 v output switch current pin 13 i sw 180 250 550 a output switch voltage pin 13 v sw 5.5 v 3) external wake-up resistor pins 3 and 17 r wu 22 k external wake-up capacitor pins 3 and 17 c wu 10 f hold time ( 30%) t h 1.5 r wu c wu s 4) delay time ( 30%) t d c wu 0.75 k s 4) 1) ic version with inverting comparator available: u4313b 2) measured at pin 9, (12) referred to 330 3) protected by a z-diode, see figure 13 4) valid for 0.1 f c wu 10 f and 22 k r wu 680 k
u4311b-fs preliminary information rev. a2, 22-sep-98 5 (13) circuit description general functions the integrated circuit u4311b includes the following functions: if amplifier, fm demodulator, wake-up circuit with monoflop, operational amplifier, non-inverting data comparator and voltage regulator. the 10.7-mhz if signal from the front end passes the integrated if amplifier which operates for amplitude- or frequency-modulated signals to either a logarithmic am demodulator which was implemented to avoid settling- time problems effected by use of an automatic gain control system or a quadrature detector for fm. a data- shaping filter advantageously realized with the internal high-performance operational amplifier reduces system bandwidth to an optimized compromise regarding transmission distance and data recognition. thus, an optimal bit-error rate can be achieved without any further active component. the comparator connected to the output of the filter has a level-dependent hysteresis and clamps its reference voltage to the signal's minimum and maximum peaks as described later. without if-input signal in normal mode only the if amplifier and the am demodulator which operates as a level-strength indicator are activated. if the level of the if signal increases, the entire circuitry is turned on by the wake-up circuit. this signal is externally available at pin 13 and can be used to wake up a microcontroller. after an adjustable reset time, determined by the mono- flop time constant, the integrated circuit returns to sleep mode. in this case, typically 1-ma supply current is re- quired. an external resistor matched at pin 3 to ground blocks the wake-up circuit and enables the complete func- tionally at lower if level as can be seen in figures 24 and 27, but supply current increases up to typically 2.8 ma. function of the clamping comparator the output signal of the operational amplifier is fed to the input of the non-inverting comparator and two peak detectors (q1 and q2, figure 3). their time constants are distinguished by rc+ and rc. the component's value must be adapted to the transmission code. the time constant should be large compared to the bit rate for opti- mized noise and hum suppression. to compensate the input transistor's base-emitter-voltage differences, these two signals are buffered by q3 and q4. the mean value is used as comparator threshold, the difference of the peak values controls the hysteresis. this clamping comparator operates as a data regenerator. 1 2 34 5 67 8 hysteresis comp. threshold comparator op. amp. + q1 q3 q4 q2 v ref to pin 20 12650 10 9 figure 3. principle function of the clamping comparator
u4311b-fs rev. a2, 22 sep-98 preliminary information 6 (13) internal pin circuitry 20 1 1251 figure 4. pin 1 op in+ 12652 17 2 v ref figure 5. pin 2 op out 17 12653 v ref 3 figure 6. pin 3 rc wake 12654 5 figure 7. pin 5 gnd2 12655 6 figure 8. pin 6 comp out 12656 7 2 17 v ref figure 9. pin 7 rc
u4311b-fs preliminary information rev. a2, 22-sep-98 7 (13) 17 12657 9 2 v ref figure 10. pin 9 rc+ 17 12658 11 v ref figure 11. pin 11 am out 12659 12 figure 12. pin 12 if in 12660 13 figure 13. pin 13 sw out 12661 15 figure 14. pin 15 gnd1 12662 16 figure 15. pin 16 discr
u4311b-fs rev. a2, 22 sep-98 preliminary information 8 (13) 17 12663 v s 19 v ref figure 16. pin 17 v ref 18 12664 v ref 17 figure 17. pin 18 fm out 12665 19 figure 18. pin 19 v s 20 1 12666 figure 19. pin 20 op in
u4311b-fs preliminary information rev. a2, 22-sep-98 9 (13) 15 20 25 30 35 0 0.001 0.002 0.003 0.004 0.005 l ( ma ) in time ( ms ) 40 95 10333 800 900 1000 1100 1200 1400 1300 v ( mv ) out output input figure 20. time domain response of 2-khz bessel lowpass data filter 6 8 10 12 14 0 20 40 60 80 100 output current ( a ) if frequency ( mhz ) 16 95 10332 100 db v 70 db v 50 db v 30 db v figure 21. if-frequency response 0.01 0.1 1 10 40 20 10 0 v / v ( db ) max frequency ( khz ) 100 95 10334 30 figure 22. frequency response of 2-khz bessel lowpass data filter data-recovering filter the test circuit in figures 23 and 26 includes an example of a data-recovering filter realized with the components r 1 , r 2 , c 1 , c 2 , c 3 . it is of a second-order bessel type with lowpass characteristic, a 3-db cut-off frequency of 2 khz and an additional highpass characteristic for suppressing dc and low-frequency ac components. simulation of time domain and frequency response can be seen in figures 20 and 22. this filter gives a typical application of a 1-kbaud manchester-code amplitude-modulated transmission. the capacitor c 2 is responsible for the highpass cut-off frequency. in order to a correct pulse response, this high- pass cut-off frequency should be as low as possible. figure 20 shows the transient response and the influence of the dc component. the first pulses might be wrong if the highpass cut-off frequency is too low. for this reason, some burst bits must be transmitted before the real data transmission starts. on the other hand, if the cut-off fre- quency is too high, roof shaping of the rectangle pulses at the operational amplifier output might cause problems. the lowpass cut-off frequency and the maximum trans- impedance v out /i in are distinguished by the further external elements. careful design of the data filter enables optimized transmission range. for designing other filter parameters,please refer to filter design hand- books/ programs or request temic for support. some proposals can be found in the application notes ant012, ant013 and ant015.
u4311b-fs rev. a2, 22 sep-98 preliminary information 10 (13) 20 19 18 17 123 4 16 15 14 56 7 13 8 r 8 r 10 c 11 c 10 c 9 r 9 c 8 v s wake-up out c 4 r 6 c 3 r 1 r 2 8.2 k 30 k c 1 10 nf c 2 100 nf 1.5 nf 100 k 100 k 100 nf 100 nf 10 nf 10 nf r 12 c 12 100 k 220 nf c 6 220 nf r 4 r 13 100 k 10 k c 5 220 nf r 7 220 k wake up 22 k r 3 data filter output r 11 10 k comparator output if input 12667 r 5 c 7 56 10 f 10 f 300 100 k 9 10 12 11 figure 23. am test circuit with 2-khz bessel lowpass data filter 80 70 60 50 40 30 20 10 0 10 0 20406080100 lp-filter output voltage vs+n/vn ( db ) if-input level ( d bv ) 95 10292 s + n n (low level) n (high level) figure 24. signal-to-noise ratio am 10 20 30 40 50 60 70 80 90 100 10 25 40 55 70 85 100 am output current ( a ) if-input level (db v ) 95 10276 +85 c +25 c 40 c figure 25. am-demodulator characteristic vs. temperature
u4311b-fs preliminary information rev. a2, 22-sep-98 11 (13) 20 19 18 17 123 4 16 15 14 56 7 13 8 r 8 r 10 c 11 c 10 c 9 r 9 c 8 v s wake-up out c 4 c 3 r 1 r 2 8.2 k 30 k c 1 10 nf 1.5 nf 100 k 100 k 100 nf 100 nf 22 pf 56 300 100 k 10 nf r 12 c 12 100 k 220 nf c 6 220 nf r 4 r 13 100 k 10 k c 5 220 nf r 7 220 k wake up 22 k r 3 data filter output r 11 10 k comparator output if input 12668 r 5 filter r 14 22 k r 15 22 k c 2 100 nf c 7 r 6 10 f 10 f toko a119acs-19000z (l = 2.2 h, c = 100 pf) 9 10 12 11 figure 26. fm test circuit with 2-khz bessel lowpass data filter 70 60 50 40 30 20 10 0 10 0 20406080100 lp-filter output voltage vs+n/vn ( db ) if-input level ( d bv ) 95 10291 s + n n figure 27. signal-to-noise ratio fm; deviation 22.5 khz 0 0.5 1.0 1.5 2.0 2.5 10.3 10.5 10.7 10.9 11.1 output voltage ( v ) frequency ( mhz ) 95 10290 c 10 = 22 pf c 10 = 47 pf figure 28. fm-discriminator characteristic
u4311b-fs rev. a2, 22 sep-98 preliminary information 12 (13) application the u4311b-fs is well-suited to implement uhf remote control or data transmission systems, based on a low- current superheterodyne receiver concept. saw-devices may be used in the transmitter's as well as in the receiver local oscillator. the front end should be a discrete circuit application with low-current uhf transistors such as temic's s822t or s852t. the frequency of the local os- cillator can be determined either by coaxial resonators or saw devices. due to the large saw-resonator, tolerance an if bandwidth and in a fm system additionally the discriminator amplitude characteristic (see figure 28) of 300 khz or higher is proposed. as the circuit needs only 3.0 v supply voltage for operation, the front end may be a stacked design in order to achieve a total receiver cur- rent consumption of approximately 1 ma. figure 29 shows a principle receiver concept diagram. the applica- tion notes ant012, ant013, and ant015 contain more detailed information on complete rf links. 350 a 350 a v s rf in 1 ma data out signal path power supply 95 10137 figure 29. principle diagram of a uhf remote control receiver package information 13007 technical drawings according to din specifications package sso20 dimensions in mm 6.75 6.50 0.25 0.65 5.85 1.30 0.15 0.05 5.7 5.3 4.5 4.3 6.6 6.3 0.15 20 11 110
u4311b-fs preliminary information rev. a2, 22-sep-98 13 (13) ozone depleting substances policy statement it is the policy of temic semiconductor gmbh to 1. meet all present and future national and international statutory requirements. 2. regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. it is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( odss). the montreal protocol ( 1987) and its london amendments ( 1990) intend to severely restrict the use of odss and forbid their use within the next ten years. various national and international initiatives are pressing for an earlier ban on these substances. temic semiconductor gmbh has been able to use its policy of continuous improvements to eliminate the use of odss listed in the following documents. 1. annex a, b and list of transitional substances of the montreal protocol and the london amendments respectively 2 . class i and ii ozone depleting substances in the clean air act amendments of 1990 by the environmental protection agency ( epa ) in the usa 3. council decision 88/540/eec and 91/690/eec annex a, b and c ( transitional substances ) respectively. temic semiconductor gmbh can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. we reserve the right to make changes to improve technical design and may do so without further notice . parameters can vary in different applications. all operating parameters must be validated for each customer application by the customer. should the buyer use temic products for any unintended or unauthorized application, the buyer shall indemnify temic against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. temic semiconductor gmbh, p.o.b. 3535, d-74025 heilbronn, germany telephone: 49 ( 0 ) 7131 67 2594, fax number: 49 ( 0 ) 7131 67 2423

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